High-speed serial data signal receiver circuitry

ABSTRACT

Circuitry for receiving a high-speed serial data signal (e.g., having a bit rate in the range of about 10 Gbps and higher) includes a two-stage, continuous-time, linear equalizer having only two serially connected stages. Phase detector circuitry may be provided for receiving the serial output of the equalizer and for converting successive pairs of bits in that output to successive parallel-form bit pairs. Further demultiplexing circuitry may be provided to demultiplex successive groups of the parallel-form bit pairs to final groups of parallel bits, which can be quite large in terms of number of bits (e.g., 64 parallel bits). Another aspect of the invention relates to multiplexer circuitry for efficiently going in the opposite direction from such relatively large groups of parallel data bits to a high-speed serial data output signal.

CROSS REFERENCE TO RELATED APPLICATION

This application is a continuation of U.S. patent application Ser. No.14/633,080 filed on Feb. 26, 2015, which is a divisional of U.S. patentapplication Ser. No. 12/002,539, filed on Dec. 17, 2007, now U.S. Pat.No. 8,989,214, which issued on Mar. 24, 2015, each of which are herebyincorporated by reference in their entirety.

BACKGROUND OF THE INVENTION

This invention relates to integrated circuit devices, and moreparticularly to circuitry on an integrated circuit that can be used toreceive a serial data signal at very high bit rates (e.g., in the rangeof about 10 gigabits per second (10 Gbps or 10G) and higher).

Industry standards have been developed that call for transmission ofserial data signals between relatively closely spaced integratedcircuits (“chips”) in a system. One typical application is the so-called10 Gigabit Small Form Factor Pluggable module. The whole modulespecification for this standard is known as XFP, and the interfacespecification for this standard is known as XFI. This module supportstelecommunication applications such as SONET OC-192 and G.709 “OUT-2,”and data communication applications such as 10 Gb/s Ethernet and 10 Gb/sFibre Channel. The serial link in this standard includes a connector anda pair of printed circuit board (“PCB”) traces of less than 200 mm. Thechannel attenuation is about 6 dB at 5.5 GHz. Providing enoughequalization and, at the same time, supporting such high data rates(i.e., in the range of about 10 Gbps and higher) in the circuitry thatreceives such a signal is a very challenging technical task.

Another challenging task is to provide good and efficient conversion ofdata from the serial form in which it is received from a channel of thetype described above to a parallel form in which it can be more easilyhandled by circuitry downstream from the receiver. A related problem isthe reverse process on the transmitter side (i.e., converting paralleldata to serial form for extremely high-speed serial output).

SUMMARY OF THE INVENTION

In accordance with one possible aspect of the invention, a high-speedserial data signal (e.g., having a bit rate in the range of about 10Gbps or higher) is received by two-stage, continuous-time, linearequalizer circuitry having only two serially connected stages. Certainparameters of these stages (e.g., their DC gain, the location in termsof frequency of a frequency response zero, and/or the location in termsof frequency of a frequency response pole) may be variable (e.g.,programmably selectable or controllable).

In accordance with another possible aspect of the invention, theequalizer output signal may be processed by half-rate, bang-bang, phasedetector circuitry. This phase detector circuitry partly deserializes ordemultiplexes the incoming data by converting successive pairs of serialdata bits to successive parallel-form bit pairs. Further multi-stagedemultiplexer circuitry may be provided for demultiplexing successivegroups of the parallel-form bit pairs to successive blocks of muchlarger numbers of parallel bits (e.g., 64 bits per block).

Still another possible aspect of the invention relates to multi-stagemultiplexer circuitry for going in the opposite direction, i.e.,converting successive relatively large blocks of parallel data bits to ahigh-speed serial data bit stream.

Further features of the invention, its nature, and various advantageswill be more apparent from the accompanying drawings and the followingdetailed description.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a simplified schematic block diagram of illustrative circuitryin accordance with the invention.

FIG. 2 is a simplified schematic block diagram of further illustrativecircuitry in accordance with the invention.

FIG. 3 is a simplified schematic block diagram of still furtherillustrative circuitry in accordance with the invention.

FIG. 4 is a simplified diagram that illustrates the flow of somerepresentative data through the FIG. 3 circuitry.

FIG. 5 is a simplified schematic block diagram of still moreillustrative circuitry in accordance with the invention.

FIG. 6 is a simplified schematic block diagram providing additionaldetail as to how certain aspects of the FIG. 1 circuitry may beconstructed.

DETAILED DESCRIPTION

An illustrative embodiment of equalizer circuitry 20 for use inhigh-speed serial data signal receiver circuitry 10 in accordance withthe invention is shown in FIG. 1. Again, the 10G receiver equalizer 20targets chip-to-chip serial link applications such as XFP/XFI. Thefunction of equalizer 20 is to reduce the demands on the phase detectorin clock and data recovery (“CDR”) circuitry that is also part ofreceiver 10. The phase detector circuitry (see FIG. 2 for anillustrative embodiment in accordance with the invention) needs toconvert the data into digital signal levels without error.

In accordance with the present invention, equalizer 20 is a two-stage,continuous-time, linear (CTL) equalizer. This architecture is relativelysimple (i.e., only two stages 30 a and 30 b), and it has relativelysmall area and low power consumption. Equalizer 20 has five poles andtwo zeros. A first pole is at the differential inputs inp and inn tofirst stage 30 a. (Inputs inp and inn are, of course, the high-speedserial data signal that has been received from a transmitting device(another chip, not shown) via a communication link (also not shown).) Asecond pole is at the differential inputs to second stage 30 b. A thirdpole is at the differential outputs outp and outn of second stage 30 b.A fourth pole (the location of which is preferably variable (e.g.,programmably variable or selectable)) is Wp of first stage 30 a. A fifthpole (the location of which is again preferably variable (e.g.,programmably variable or selectable)) is Wp of second stage 30 b. Afirst zero (the location of which is preferably variable (e.g.,programmably variable or selectable)) is Wz of first stage 30 a. Asecond zero (the location of which is also preferably variable (e.g.,programmably variable or selectable)) is Wz of second stage 30 b.(“Location” in the preceding sentences means position of Wp or Wz interms of frequency along the frequency axes shown in FIG. 1).

In FIG. 1 the symbol for each of stages 30 a and 30 b contains a diagramshowing the (parameterized) frequency response of that stage. Thedepicted frequency response parameters are DC gain, AC gain, zerolocation Wz, pole location Wp, and upward slope of the start of theequalizing region (i.e., the region of AC gain between Wz and Wp). Inaddition to Wz and Wp for each stage 30 being preferably variable, theamount of DC gain of each stage 30 is also preferably variable (e.g.,programmably variable or selectable). The slope and AC gain parametersof each stage 30 may not be independently variable, but may depend onother factors such as the position of the zero (Wz) of that stage.

Equalizer 20 has only two stages 30 a and 30 b because it is intendedfor operation in a relatively narrow frequency band (e.g., to supportnarrow-band 10G operation). In the type of chip-to-chip (e.g., XFP/XFI)operation that equalizer 20 is designed to support there is less lossthan in other types of applications such as those involving a backplanecommunication link between the transmitting device and the receivingdevice. In such backplane applications (which may operate, for example,at 6 Gbps) there can be much greater loss and therefore a need for morethan two stages in the receiver equalizer. More than two receiverequalizer stages are undesirable in the type of relatively low-loss,chip-to-chip application of interest in connection with the presentinvention because more than two equalizer stages tend to amplify noisetwo much. Overall, equalizer 20 may typically provide up to 6 dB gainboost at 5.5 GHz to compensate for the signal across the channel fromthe transmitting device (not shown) to receiver 10. Although theintended range of operation of equalizer 20 is (as noted above)relatively narrow around 10 Gbps, the circuitry can also supportsomewhat higher frequencies (e.g., up to about 11.3 Gbps).

Downstream from equalizer 20 in receiver circuitry 10 is a phasedetector, which can be constructed as shown at 40 in FIG. 2 inaccordance with further aspects of the invention. The differential inputsignals inp and inn to phase detector 40 in FIG. 2 are the differentialoutput signals outp and outn in FIG. 1. The phase detector is animportant high-speed block in CDR circuitry that forms part of ahigh-speed serial data signal receiver. Phase detector 40 takes theoutput from equalizer 20 and coverts it to the binary output (Dodd andDeven). Phase detector 40 also compares the phase differences between(1) a recovered clock signal from a voltage-controlled oscillator(“VCO”) in the CDR circuitry and (2) the equalized input data. Thedetected phase differences (lead and lag) help the VCO to synchronizethe embedded clock information in the input data signal.

To accommodate the high data rate, 10G phase detector 40 uses ahalf-rate, bang-bang structure. This structure includes four, binary,high-speed comparators or samplers 42 a-d. Each of samplers 42 is drivenby a respective one of four quadrature clocks from the above-mentionedVCO. In particular, sampler 42 a is driven by the clock signal havingrelative phase 0°; sampler 42 b is driven by the clock signal havingrelative phase 90°; sampler 42 c is driven by the clock signal havingrelative phase 270°; and sampler 42 d is driven by the clock signalhaving relative phase 180°. It will thus be seen that the quadratureclock signals have phases that are equally distributed or spaced acrossone complete clock cycle (360°). Each sampler 42 samples thedifferential data signals that it receives in synchronism with therising edge in the clock signal applied to it. If when such a sample istaken by a sampler 42, the plus input to that sampler has higher voltagethan the minus input, then the sampler outputs a binary 1 signal. On theother hand, if when such a sample is taken by a sampler 42, the plusinput to that sampler has lower voltage than the minus input, then thesampler outputs a binary 0 signal. Note that the frequency of the clocksignals is half the serial data rate (i.e., one complete cycle of theclock signals occupies the same amount of time as two successive unitintervals (data bit durations) of the high-speed serial data inputsignal). Sampler 42 a should therefore be sampling near the middle ofsuccessive odd-numbered bits in the serial data input signal, whilesampler 42 c should be sampling near the middle of successiveeven-numbered bits in the serial data input signal. Sampler 42 a shouldaccordingly be able to produce the Dodd output signal (i.e., a binarydata output signal indicative of the odd-numbered data bits in theserial data input signal), while sampler 43 c should be able to producethe Deven output signal (i.e., a binary data output signal indicative ofthe even-numbered data bits in the serial data input signal).

Logic block 44 receives the output signals of all four samplers 42 a-dto generate signals (lead and lag) indicative of how close to thecenters of the odd and even bits samplers 42 a and 42 c are in factsampling. For example, if samplers 42 a and 42 c are sampling earlierthan the centers of the odd and even bits, then the outputs of samplers42 a and 42 b will always be the same (because both of these samplersare sampling in the same unit interval of the serial data input signal),and the outputs of samplers 42 c and 42 d will also always be the same.Logic block 44 can detect this condition and can output a pulse on its“lead” output lead to indicate that the VCO clock signals are leadingthe phase that they should have for optimal sampling of the serial datainput signal. Such a “lead” output pulse can be used to cause the VCO toslow down slightly in terms of frequency to improve the phasing of thequadrature clock signals produced by the VCO. Conversely, if samplers 42a and 42 c are sampling the serial data input signal later than thecenters of data bits in that signal, then the outputs of samplers 42 aand 42 b will frequently be different from one another (because thesetwo samplers are sampling in two successive unit intervals in theincoming serial data signal), but the outputs of samplers 42 b and 42 cwill always be the same. Similar behavior will be found in comparisonsof the outputs of samplers 42 c and 42 d (frequently different) and 42 dand 42 a (always the same). Logic block 44 can detect this condition andcan output a pulse on its “lag” output lead to indicate that the VCOclock signals are lagging the phase that they should have for optimalsampling of the serial data signal. Such a “lag” output pulse can beused to cause the VCO to speed up slightly in terms of frequency toimprove the phasing of the quadrature clock signals produced by the VCO.

Like equalizer 20, the intended range of operation of phase detector 40is around 10 Gbps, but it can also support somewhat higher frequencies(e.g., up to about 11.3 Gbps).

Each high-speed comparator 42 in phase detector 40 preferably hasbuilt-in offset cancellation circuitry. This offset cancellationcircuitry may be set by means of a calibration operation that isperformed prior to normal operation of the circuitry to process anactual serial data signal. This calibration operation preferably giveseach comparator 42 a threshold of 0 volts. Thereafter, each comparatorlooks for a positive difference between the plus and minus inputs tothat comparator, and produces a binary 1 output when that difference ispositive (i.e., greater than the 0 volt threshold that has beenestablished for that comparator).

Recapitulating some of the benefits and advantages of the foregoing,programmable zeros Wz in the receiver equalizer 20 boost the receivergain up to about 6 dB at 5.5 GHz. The CTL equalizer structure 20 has lowpower and small area. Both the equalizer 20 and the phase detector 40support data rates up to about 11.3 Gbps. Offset cancellation withinphase detector 40 increases the 10G receiver input sensitivity.

We turn now to possible de-serializer (and converse serializer) aspectsof the invention.

As has been mentioned, 10 Gbps electrical high-speed serial (“HSS”)transceivers are desired in many applications such as OC192SONET/SDH, 10Gbit Ethernet, Optical Transport Networks, and/or systems with forwarderror correction, etc. While the HSS link (e.g., as shown in FIGS. 1 and2 herein) provides very high throughputs at the chip pin point, othercircuitry that needs to use (or supply) these signals (e.g., theremaining circuitry of a programmable microcontroller, afield-programmable gate array (“FPGA”), or core logic of some other typeof integrated circuit device that includes the HSS circuitry) may stillprocess data in parallel at lower clock rates for better signalintegrity and time margin. Thus the HSS receiver like 10 herein (or acomparable HSS transmitter like that shown, for example, in Wong et al.U.S. patent application Ser. No. 12/002,540) filed Dec. 17, 2007 needsto convert the serial data to parallel data (or to do the opposite onthe transmitter side). The present disclosure provides 1:64 deserializercircuitry and 64:1 serializer circuitry that can be used for thesepurposes.

An illustrative embodiment of deserializer circuitry 100 in accordancewith the invention is shown in FIG. 3. This circuitry has a first stagethat includes two 1:4 demultiplexers 110 a and 110 b, and a second stagethat includes eight 1:8 demultiplexers 120 a-h. Demultiplexer 110 areceives the Deven output signal of circuitry 40. In parallel with this,demultiplexer 110 b receives the Dodd output signal of circuitry 40.Demultiplexers 110 a-b also receive a half-rate clock signal having (1)the same frequency as any of the phase 0 to phase 270 signals in FIG. 2,and (2) phase that is appropriate for allowing demultiplexers 110 a-110b to latch in successive pairs of valid Deven and Dodd signals as willbe described in more detail below. The output side of this first stageof the deserializer is clocked by a clock signal having frequencydivided by 4 (by frequency divider 112) from the half-rate frequencyused to clock in the input side of this deserializer stage.

Demultiplexers 110 a-b produce eight parallel output signals, each ofwhich is applied to a respective one of the eight demultiplexers 120a-h. The input side of demultiplexers 120 a-h is clocked by a signalhaving the same frequency as is used to clock the output side ofdemultiplexers 110 a-b. Demultiplexers 120 a-h eventually accumulate 64bits of valid data and output that data in parallel on the Dout leads.The output side of this second stage of the deserializer is clocked by aclock signal having frequency divided by 8 (by frequency divider 122)from the frequency used to clock the input side of this deserializerstage. This clock signal (CLK_DIVRX) can also be applied to downstreamcircuitry to allow that circuitry to latch in valid Dout signals.

FIG. 4 illustrates how data may flow through demultiplexers 110 a-b and120 a-h. In a first period of a half-rate clock (i.e., half the incomingserial bit rate), the first two serial bits to arrive (arbitrarilyreferred to as bits 0 and 1) are stored in demultiplexers 110 a and 110b, respectively. In a second period of the above-mentioned half-rateclock, the next two serial bits to arrive (i.e., bits 2 and 3) arestored in demultiplexers 110 a and 110 b, respectively. In a thirdperiod of the half-rate clock, the next two bits to arrive serially(i.e., bits 4 and 5) are added to what is stored in demultiplexers 110 aand 110 b, respectively. In a fourth half-rate clock period, bits 6 and7 are added to what is stored in demultiplexers 110 a and 110 b,respectively. The contents of demultiplexers 110 are then transferred todemultiplexers 120 a-h. In particular, bit 0 is transferred fromdemultiplexer 110 a to demultiplexer 120 a, where bit 0 is now stored;bit 1 goes from demultiplexer 110 b to demultiplexer 120 b, where bit 1is now stored; bit 2 goes from 110 a to 120 c, where bit 2 is nowstored; bit 3 goes from 110 b to 120 d, where bit 3 is now stored; andso on. In successive periods of the half-rate clock, multiplexers 110 aand b are again filled with data from circuitry 40. Then this data isagain transferred to demultiplexers 120 a-h so that 120 a stores bits 0and 8, 120 b stores bits 1 and 9, 120 c stores bits 2 and 10, 120 dstores bits 3 and 11, and so on.

The above-described process continues until demultiplexers 120 a-h arefull (e.g., 120 a contains bits 0, 8, 16, 24, 32, 40, 48, and 56). Alleight of demultiplexers 120 a-h then output all of their data inparallel on leads Dout. This parallel data can go to downstreamcircuitry which can process it at much lower data rates than the serialdata rate. For example, this downstream circuitry can process thisparallel data using a parallel data clock (like CLK_DIVRX) that isone-sixty-fourth (1/64) the incoming serial bit rate. This greatlyfacilitates the design, construction, and operation of the downstreamcircuitry (sometimes referred to as utilization circuitry).

It will be noted that even within demultiplexer 100, the construction ofthat circuitry helps it operate at clock signal frequencies that arelower than the serial bit rate. For example, each of demultiplexers 110a and 110 b only has to receive data at one-half the serial bit rate.This is so because upstream circuitry 40 already puts two seriallyreceived bits in parallel (effectively cutting the data rate to one-halfthe serial bit rate). Demultiplexers 110 a and 110 b collectively outputeight bits in parallel. Therefore their output data rate (and the inputdata rate of demultiplexers 120 a-h) is one-eighth the serial bit rate.And of course the output data rate of demultiplexers 120 a-h isone-sixty-fourth the serial bit rate.

Illustrative multiplexer circuitry 200 in accordance with anotherpossible aspect of the invention is shown in FIG. 5. The circuitryupstream from this circuitry can be part of the circuitry that isdownstream from the circuitry shown in FIG. 3 herein. The circuitrydownstream from the FIG. 5 circuitry can be transmitter driver circuitry(e.g., like that shown in the above-mentioned Wong et al. reference).

Multiplexer 210 can receive 64 bits of data in parallel via theDATA_IN[63:0] leads. Multiplexer 210 also receives a clock signal havingfrequency and phase that allows multiplexer 210 to latch each successiveblock of 64 valid data bits that it receives.

Multiplexer 210 outputs the 64 data bits that it has received in eightblocks of eight parallel bits each. For example, if the bits thatmultiplexer 210 has received are arbitrarily numbered 0-63, then bits0-7 are output first; then bits 8-15 are output; then bits 16-23 areoutput; and so on. These 8-bit blocks are output at eight times thefrequency that the 64-bit blocks are applied to multiplexer 210.

The even-numbered bits in each 8-bit block output by multiplexer 210 areall applied in parallel to multiplexer 220 a. The odd-numbered bits ineach such 8-bit block are all applied in parallel to multiplexer 220 b.Thus, for example, from the 8-bit block that includes bits 0-7, bits 0,2, 4, and 6 are all applied to multiplexer 220 a, and bits 1, 3, 5, and7 are all applied to multiplexer 220 b.

Each of multiplexers 220 a and 220 b outputs the four bits that itreceives in parallel one after another in series. Note, however that thetwo series output by multiplexers 220 a and 220 b are synchronized withone another so that they collectively constitute two data streams thatare in parallel with one another. These two data streams are applied inparallel to the input side of multiplexer 230. Because the successiveoutputs of multiplexer 220 a are all even bits, while the successiveoutputs of multiplexer 220 b are all odd bits, multiplexer 230 receivesone even bit and one odd bit in each cycle of operation of its inputside.

Multiplexer 230 outputs each pair of bits (which it has received inparallel) one after another in series. Accordingly, multiplexer 230produces the final serial data output stream TX_DATA.

Clocking of the output side of multiplexer 230 is typically at theserial bit rate (e.g., about 10 Gbps or higher). Clocking of the inputside of multiplexer 230 (and the output side of multiplexers 220) can beat one-half the serial bit rate. Clocking of the input side ofmultiplexers 220 (and the output side of multiplexer 210) can be atone-eighth the serial bit rate. Clocking of the input side ofmultiplexer 210 can be at one-sixty-fourth the serial bit rate. Some orall of the necessary clock signals can be provided by appropriatemultiplication of the frequency of the CLK input to multiplexer 200.Alternatively or in addition, some or all of the necessary clock signalscan be provided by appropriately dividing the frequency of a serial bitrate clock signal (e.g., supplied from a reference clock signal source240). For completeness, an example in which all of the clock signals(except for the input side of mux 210) are provided from such ahigh-speed reference clock signal source 240 is shown in FIG. 5. In thisexample, source 240 clocks the output side of mux 230. Frequency divider242 divides the reference clock frequency by 2 to clock the input sideof mux 230 and the output side of muxes 220. Frequency divider 244divides the element 242 output frequency by 4 to clock the input side ofmuxes 220 and the output side of mux 210.

Note that the multiplexer structure shown in FIG. 5 allows the upstreamcircuitry to operate at relatively low clock rates (e.g.,one-sixty-fourth the serial output bit rate). The FIG. 5 circuitry canaccept this data at such a relatively low clock rate, and can thenconvert it to serial data having a very high serial data rate. Inaddition, the FIG. 5 circuitry has the advantage of not needing to workwith the very high serial data rate until the final, relatively small2:1 multiplexer 230 is reached. Only the output side of this relativelysmall multiplexer 230 has to operate at the very high serial bit rate.The input side of mux 230 operates at one-half the serial bit rate, andthe upstream stages of multiplexer 200 operate at that reduced rate oreven further reduced rates. Another advantage of the circuitry of FIG. 5is that two 4:1 muxes 220 a and 220 b are provided and operate inparallel. The input clocking and phasing of both of these components 220can be the same. The output clocking and phasing of both of thesecomponents can also be the same. In addition, the output clocking ofthese relatively large (as compared to mux 230) multiplexers 220 can beat lower frequency than the final serial output data bit rate.

FIG. 6 recapitulates, amplifies, and depicts the point made earlier thatthe values of variable parameters of equalizer stage 30 a and/or 30 b(e.g., the DC gain, the location in frequency of the variable zero Wz,and/or the location in frequency of the variable pole Wp of either orboth of those stages) can be programmably controlled. Thus FIG. 6 showsthat any or all of these parameters can be controlled by programmablememory 300, which can be part of the integrated circuit device thatincludes the other circuitry such as 10 that is shown and describedherein. For example, this integrated circuit may be or may includeprogrammable circuitry such as a programmable microcontroller, aprogrammable logic device (“PLD”), etc. In such cases, memory 300 may bepart of the programmable configuration memory of the programmableintegrated circuit device.

It will be understood that the foregoing is only illustrative of theprinciples of the invention, and that various modifications can be madeby those skilled in the art without departing from the scope and spiritof the invention.

What is claimed is:
 1. Receiver circuitry, comprising: phase detectorcircuitry that receives serial data at a first data rate, the phasedetector circuitry comprising: a first comparator that receives theserial data and outputs even-numbered data bits of the serial data basedat least in part on a first clock signal having a frequency that is halfof the first data rate; a second comparator that receives the serialdata and outputs odd-numbered data bits of the serial data set of databits of the serial data based at least in part on a second clock signalhaving a first phase offset from the first clock signal; a thirdcomparator that receives the serial data and provides a first set ofdata bits of the serial data based at least in part on a third clocksignal having a second phase offset from the first clock signal; afourth comparator that receives the serial data and provides a secondset of data bits of the serial data based at least in part on a fourthclock signal having a third phase offset from the first clock signal;and logic circuitry that determines a phase difference between the firstclock signal and the serial data based at least in part on theeven-numbered data bits, the odd-numbered data bits, the first set ofdata bits, and the second set of data bit, and outputs a lead signal ora lag signal based at least in part on the determination of the phasedifference.
 2. The receiver circuitry of claim 1, wherein the firstclock signal comprises a recovered clock signal recovered from theserial data.
 3. The receiver circuitry of claim 1, wherein a phase ofthe first clock signal is adjusted based at least in part on the lagsignal or the lead signal.
 4. The receiver circuitry of claim 1, whereinthe even numbered data bits and the odd-numbered data bits are providedas a pair of parallel data bits.
 5. The receiver circuitry of claim 1,wherein the first phase difference is a 180° phase difference, thesecond phase difference is a 90° phase difference, and the third phasedifference is a 270° phase difference.
 6. The receiver circuitry ofclaim 1, wherein the logic circuitry determines the phase difference bycomparing the even-numbered data bits with the first set of data bitsand with the second set of data bits.
 7. The receiver circuitry of claim1, wherein received serial data is a differential signal serial data. 8.A method to convert differential input signals into binary output, themethod comprising: receiving a differential serial data signal from aclock-and-data recovery at a data rate; obtaining a first clock signalhaving a frequency that is half the data rate; obtaining aneven-numbered binary output by sampling the differential serial datasignal and using the first clock signal; obtaining an odd-numberedbinary output by sampling the differential serial data signal using asecond clock signal that has a first phase difference from the firstclock signal; obtaining a first set of data bits by sampling thedifferential serial data signal using a third clock signal that has asecond phase difference from the first clock signal; obtaining an secondset of data bits by sampling the differential serial data signal using afourth clock signal that has a third phase difference from the firstclock signal; and adjusting a phase of the first clock signal based atleast in part on a phase offset between the first clock signal and theserial data signal based at least in part on a comparison between theeven-numbered binary output, the odd-numbered binary output, the firstset of data bits, and the second set of data bits.
 9. The method ofclaim 8, wherein determining the phase offset comprises providing a leadsignal output or a lag signal output.
 10. The method of claim 8, whereinadjusting the phase of the first clock signal comprises adjusting avoltage-controlled oscillator of the clock-and-data recovery circuitry.11. The method of claim 8, wherein generating the even-numbered binaryoutput comprises using a first comparator that receives the differentialserial data signal and the first clock signal, generating theodd-numbered binary output comprises using a second comparator thatreceives the differential serial data signal and the second clocksignal.
 12. The method of claim 8, wherein the first phase difference isa 180° phase difference, the second phase difference is a 90° phasedifference, and the third phase difference is a 270° phase difference.13. A system comprising: a continuous-time equalizer, wherein thelocation of at least one zero of the equalizer and at least one pole ofthe equalizer is controlled by programmable memory, and wherein theequalizer receives a differential serial signal and provides anequalized differential serial signal; phase detector circuitry thatreceives the equalized differential serial signal at a first frequency,generates even-numbered data bits using a first clock signal having asecond frequency that is half the frequency of the first frequency,generates odd-numbered data bits using a second clock signal having thesecond frequency, and provide the even-numbered data bits and theodd-numbered data bits as a pair of parallel data bits; anddemultiplexer circuitry that receives the pair of parallel data bits andthe first clock signal, and provides a parallel data signal, wherein thedemultiplexer circuitry comprises: a first stage comprising one or moredemultiplexers that produce intermediate blocks of parallel data bitsfrom the pair of parallel data bits and are clocked by a third clocksignal that is produced using the first clock signal; and a second stagecomprising one or more demultiplexers that output the parallel datasignal from the intermediate blocks of parallel data bits and areclocked by a fourth clock signal that is produced using the third clocksignal.
 14. The system of claim 13, wherein the equalizer comprises twoserially connected stages, and wherein an AC gain parameter of each ofthe first and the second stage depends on the at least one zero.
 15. Thesystem of claim 13, wherein the equalizer has five poles and no morethan four zeros, two of the poles are controlled by the programmablememory, all zeros are controlled by the programmable memory, and two ofthe poles are fixed.
 16. The system of claim 13, wherein the equalizerprovides up to 6 DB gain boost at 5.5 GHz.
 17. The system of claim 13,wherein: the first clock is based at least in part on avoltage-controlled oscillator of the system; the phase detectorcircuitry provides a lag signal or a lead signal based at least in parton a phase difference between the equalized differential signal and thefirst clock; and the voltage-controlled oscillator adjusts the firstclock based at least in part on the lag signal or the lead signal. 18.The system of claim 13, wherein: the third clock has a frequency that isone quarter of that of the first clock; a width of the intermediateblocks of parallel data bits is 8 bits; the fourth clock has a frequencythat is one eight of that of the third clock; and a width of theparallel data signal is 64 bits.
 19. The system of claim 13, comprisingcustom logic that receives the parallel data signal.
 20. The system ofclaim 19, wherein the custom logic provides outgoing parallel datasignal; and wherein the system comprises multiplexer circuitry thatreceives the outgoing parallel data signal clocked by a first outputclock signal and provides outgoing serial data signal, wherein themultiplexer circuitry comprises: a first stage comprising one or moremultiplexers that produce intermediate blocks of outgoing parallel databits using the outgoing parallel data signal and are clocked by a secondoutput clock signal that is produced from a transmitting circuitryreference clock; and a second stage comprising one or more multiplexersthat output the outgoing serial data signal from the intermediate blocksof outgoing parallel data bits and are clocked by a third clock signalthat is produced using the transmitting circuitry reference clock.